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FEATURES ■ Outputs May be Paralleled for Higher Current and Heat Spreading ■ Output Current: 1.1A ■ Single Resistor Programs Output Voltage ■ 1% Initial Accuracy of SET Pin Current ■ Output Adjustable to 0V ■ Low Output Noise: 40μVRMS (10Hz to 100kHz) ■ Wide Input Voltage Range: 1.2V to 36V ■ Low Dropout Voltage: 300mV ■ <1mV Load Regulation ■ <0.001%/V Line Regulation ■ Minimum Load Current: 0.5mA ■ Stable with 2.2μF Minimum Ceramic Output Capacitor ■ Current Limit with Foldback and Overtemperature Protected ■ Available in 8-Lead MSOP, 3mm × 3mm DFN, 5-Lead TO-220 and 3-Lead SOT-223 U APPLICATIO S ■ High Current All Surface Mount Supply ■ High Efficiency Linear Regulator ■ Post Regulator for Switching Supplies ■ Low Parts Count Variable Voltage Supply ■ Low Output Voltage Power Supplies TYPICAL APPLICATIO Variable Output Voltage 1.1A Supply VIN 1.2V TO 36V IN VCONTROL 1μF LT3080 + – OUT SET RSET VOUT = RSET • 10μA 3080 TA01a VOUT 2.2μF U U LT3080 Adjustable1.1A Single Resistor Low Dropout Regulator DESCRIPTIO The LT®3080 is a 1.1A low dropout linear regulator that can be paralleled to increase output current or spread heat in surface mounted boards. Architected as a precision current source and voltage follower allows this new regulator to be used in many applications requiring high current, adjustability to zero, and no heat sink. Also the device brings out the collector of the pass transistor to allow low dropout operation —down to 300 millivolts— when used with multiple supplies. A key feature of the LT3080 is the capability to supply a wide output voltage range. By using a reference current through a single resistor, the output voltage is programmed to any level between zero and 36V. The LT3080 is stable with 2.2μF of capacitance on the output, and the IC uses small ceramic capacitors that do not require additional ESR as is common with other regulators. Internal protection circuitry includes current limiting and thermal limiting. The LT3080 regulator is offered in the 8-lead MSOP (with an Exposed Pad for better thermal characteristics), a 3mm × 3mm DFN, 5-lead TO-220 and a simple-to-use 3-lead SOT-223 version. , LT, LTC and LTM are registered trademarks of Linear Technology Corporation. All other trademarks are the property of their respective owners. Set Pin Current Distribution N = 13792 9.80 9.90 10.00 10.10 10.20 SET PIN CURRENT DISTRIBUTION (μA) 3080 G02 3080f 1 LT3080 U WW W ABSOLUTE AXI U RATI GS (Note 1)(All Voltages Relative to VOUT) VCONTROL Pin Voltage..................................... 40V, –0.3V IN Pin Voltage ................................................ 40V, –0.3V SET Pin Current (Note 7) .....................................±10mA SET Pin Voltage (Relative to OUT) .........................±0.3V Output Short-Circuit Duration .......................... Indefinite Operating Junction Temperature Range (Notes 2, 10).......................................... –40°C to 125°C Storage Temperature Range:.................. –65°C to 150°C Lead Temperature (Soldering, 10 sec) MS8E, T and ST Packages Only ........................ 300°C PIN CONFIGURATION TOP VIEW OUT 1 8 IN OUT 2 7 IN 9 OUT 3 6 NC SET 4 5 VCONTROL DD PACKAGE 8-LEAD (3mm × 3mm) PLASTIC DFN TJMAX = 125°C, θJA = 64°C/W, θJC = 3°C/W EXPOSED PAD (PIN 9) IS OUT, MUST BE SOLDERED TO PCB TAB IS OUT FRONT VIEW 5 4 3 2 1 T PACKAGE 5-LEAD PLASTIC TO-220 TJMAX = 125°C, θJA = 40°C/W, θJC = 3°C/W IN VCONTROL OUT SET NC TOP VIEW OUT 1 8 IN OUT 2 OUT 3 9 7 IN 6 NC SET 4 5 VCONTROL MS8E PACKAGE 8-LEAD PLASTIC MSOP TJMAX = 125°C, θJA = 60°C/W, θJC = 10°C/W EXPOSED PAD (PIN 9) IS OUT, MUST BE SOLDERED TO PCB TAB IS OUT FRONT VIEW 3 IN* 2 OUT 1 SET ST PACKAGE 3-LEAD PLASTIC SOT-223 *IN IS VCONTROL AND IN TIED TOGETHER TJMAX = 125°C, θJA = 55°C/W, θJC = 15°C/W ORDER INFORMATION LEAD FREE FINISH TAPE AND REEL PART MARKING PACKAGE DESCRIPTION LT3080EDD#PBF LT3080EDD#TRPBF LCBN 8-Lead (3mm × 3mm) Plastic DFN LT3080EMS8E#PBF LT3080EMS8E#TRPBF LTCBM 8-Lead Plastic MSOP LT3080ET#PBF LT3080ET#TRPBF LT3080ET 5-Lead Plastic TO-220 LT3080EST#PBF LT3080EST#TRPBF 3080 3-Lead Plastic SOT-223 LEAD BASED FINISH TAPE AND REEL PART MARKING PACKAGE DESCRIPTION LT3080EDD LT3080EDD#TR LCBN 8-Lead (3mm × 3mm) Plastic DFN LT3080EMS8E LT3080EMS8E#TR LTCBM 8-Lead Plastic MSOP LT3080ET LT3080ET#TR LT3080ET 5-Lead Plastic TO-220 LT3080EST LT3080EST#TR 3080 3-Lead Plastic SOT-223 Consult LTC Marketing for parts specified with wider operating temperature ranges. For more information on lead free part marking, go to: http://www.linear.com/leadfree/ For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/ 2 TEMPERATURE RANGE –40°C to 125°C –40°C to 125°C –40°C to 125°C –40°C to 125°C TEMPERATURE RANGE –40°C to 125°C –40°C to 125°C –40°C to 125°C –40°C to 125°C 3080f LT3080 ELECTRICAL CHARACTERISTICS The ● denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. (Note 11) PARAMETER CONDITIONS MIN TYP MAX UNITS SET Pin Currrent ISET Output Offset Voltage (VOUT – VSET) VOS VIN = 1V, VCONTROL = 2V, IOUT = 1mA VIN = 1V, VCONTROL = 2.0V, ILOAD = 1mA, TJ = 25°C VIN ≥ 1V, VCONTROL ≥ 2.0V, 1mA ≤ ILOAD ≤ 1.1A (Note 9) DFN and MSOP Package SOT-223 and T0-220 Package 9.90 10 10.10 μA ● 9.80 10 10.20 μA –2 ● –3.5 2 mV 3.5 mV –5 ● –6 5 mV 6 mV Load Regulation ΔISET ΔILOAD = 1mA to 1.1A ΔVOS ΔILOAD = 1mA to 1.1A (Note 8) – 0 .1 nA ● 0.6 1.3 mV Line Regulation (Note 9) DFN and MSOP Package ΔISET VIN = 1V to 25V, VCONTROL=1V to 25V, ILOAD=1mA ΔVOS VIN = 1V to 25V, VCONTROL=1V to 25V, ILOAD=1mA ● 0.1 0.5 nA/V 0.003 mV/V Line Regulation (Note 9) SOT-223 and TO-220 Package ΔISET VIN = 1V to 26V, VCONTROL=1V to 26V, ILOAD=1mA ΔVOS VIN = 1V to 26V, VCONTROL=1V to 26V, ILOAD=1mA ● 0.1 0.5 nA/V 0.003 mV/V Minimum Load Current (Notes 3, 9) VIN = VCONTROL = 10V VIN = VCONTROL = 25V (DFN and MSOP Package) VIN = VCONTROL = 26V (SOT-223 and TO-220 Package) ● 300 500 μA ● 1 mA ● 1 mA VCONTROL Dropout Voltage (Note 4) ILOAD = 100mA ILOAD = 1.1A 1.2 V ● 1.35 1.6 V VIN Dropout Voltage (Note 4) ILOAD = 100mA ILOAD = 1.1A ● 100 200 mV ● 350 500 mV CONTROL Pin Current ILOAD = 100mA ILOAD = 1.1A ● 4 6 mA ● 17 30 mA Current Limit VIN = 5V, VCONTROL = 5V, VSET = 0V, VOUT = –0.1V ● 1.1 1.4 A Error Amplifier RMS Output Noise (Note 6) ILOAD = 1.1A, 10Hz ≤ f ≤ 100kHz, COUT = 10μF, CSET = 0.1μF 40 μVRMS Reference Current RMS Output Noise (Note 6) 10Hz ≤ f ≤ 100kHz 1 nARMS Ripple Rejection f = 120Hz, VRIPPLE = 0.5VP-P, ILOAD = 0.2A, CSET = 0.1μF, COUT = 2.2μF f = 10kHz f = 1MHz 75 dB 55 dB 20 dB Thermal Regulation, ISET 10ms Pulse 0.003 %/W Note 1: Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. Exposure to any Absolute Maximum Rating condition for extended periods may affect device reliability and lifetime. Note 2: Unless otherwise specified, all voltages are with respect to VOUT. The LT3080 is tested and specified under pulse load conditions such that TJ ≈ TA. The LT3080 is 100% tested at TA = 25°C. Performance at –40°C and 125°C is assured by design, characterization and correlation with statistical process controls. Note 3: Minimum load current is equivalent to the quiescent current of the part. Since all quiescent and drive current is delivered to the output of the part, the minimum load current is the minimum current required to maintain regulation. Note 4: For the LT3080, dropout is caused by either minimum control voltage (VCONTROL) or minimum input voltage (VIN). Both parameters are specified with respect to the output voltage. The specifications represent the minimum input-to-output differential voltage required to maintain regulation. Note 5: The CONTROL pin current is the drive current required for the output transistor. This current will track output current with roughly a 1:60 ratio. The minimum value is equal to the quiescent current of the device. Note 6: Output noise is lowered by adding a small capacitor across the voltage setting resistor. Adding this capacitor bypasses the voltage setting resistor shot noise and reference current noise; output noise is then equal to error amplifier noise (see Applications Information section). Note 7: SET pin is clamped to the output with diodes. These diodes only carry current under transient overloads. Note 8: Load regulation is Kelvin sensed at the package. Note 9: Current limit may decrease to zero at input-to-output differential voltages (VIN–VOUT) greater than 25V (DFN and MSOP package) or 26V (SOT-223 and TO-220 package). Operation at voltages for both IN and VCONTROL is allowed up to a maximum of 36V as long as the difference between input and output voltage is below the specified differential (VIN– VOUT) voltage. Line and load regulation specifications are not applicable when the device is in current limit. Note 10: This IC includes over-temperature protection that is intended to protect the device during momentary overload conditions. Junction temperature will exceed the maximum operating junction temperature when over-temperature protection is active. Continuous operation above the specified maximum operating junction temperature may impair device reliability. Note 11: The SOT-223 package connects the IN and VCONTROL pins together internally. Therefore, test conditions for this pin follow the VCONTROL conditions listed in the Electrical Characteristics Table. 3080f 3 SET PIN CURRENT (μA) LT3080 TYPICAL PERFOR A CE CHARACTERISTICS UW Set Pin Current 10.20 10.15 10.10 10.05 10.00 9.95 9.90 9.85 9.80 –50 –25 0 25 50 75 100 125 150 TEMPERATURE (°C) 3080 G01 Set Pin Current Distribution N = 13792 9.80 9.90 10.00 10.10 10.20 SET PIN CURRENT DISTRIBUTION (μA) 3080 G02 OFFSET VOLTAGE (mV) Offset Voltage (VOUT – VSET) 2.0 IL = 1mA 1.5 1.0 0.5 0 –0.5 –1.0 –1.5 –2.0 –50 –25 0 25 50 75 100 125 150 TEMPERATURE (°C) 3080 G03 Offset Voltage Distribution N = 13250 –2 –1 0 1 2 VOS DISTRIBUTION (mV) 3080 G04 Load Regulation 0 20 ΔILOAD = 1mA TO 1.1A –0.1 VIN – VOUT = 2V 10 CHANGE IN REFERENCE CURRENT –0.2 0 –0.3 –10 CHANGE IN OFFSET VOLTAGE –0.4 –20 –0.5 (VOUT – VSET) –30 –0.6 –40 –0.7 –50 –0.8 –50 –25 –60 0 25 50 75 100 125 150 TEMPERATURE (°C) 3080 G07 CHANGE IN REFERENCE CURRENT WITH LOAD (nA) OFFSET VOLTAGE (mV) MINIMUM LOAD CURRENT (mA) Offset Voltage 1.00 ILOAD = 1mA 0.75 0.50 0.25 0 –0.25 –0.50 –0.75 –1.00 0 6 12 18 24 30 36* INPUT-TO-OUTPUT VOLTAGE (V) *SEE NOTE 9 IN ELECTRICAL CHARACTERISTICS TABLE 3080 G05 Minimum Load Current 0.8 0.7 0.6 VIN, CONTROL – VOUT = 36V* 0.5 0.4 VIN, CONTROL – VOUT = 1.5V 0.3 0.2 0.1 0 –50 –25 0 25 50 75 100 125 150 TEMPERATURE (°C) *SEE NOTE 9 IN ELECTRICAL CHARACTERISTICS TABLE 3080 G08 OFFSET VOLTAGE (mV) MINIMUM IN VOLTAGE (VIN – VOUT) (mV) Offset Voltage 0.25 0 –0.25 TJ = 25°C –0.50 –0.75 TJ = 125°C –1.00 –1.25 –1.50 –1.75 0 0.2 0.4 0.6 0.8 1.0 1.2 LOAD CURRENT (A) 3080 G06 Dropout Voltage (Minimum IN Voltage) 400 350 TJ = 125°C 300 250 TJ = 25°C 200 150 100 50 0 0 0.2 0.4 0.6 0.8 1.0 1.2 OUTPUT CURRENT (A) 3080 G09 CHANGE IN OFFSET VOLTAGE WITH LOAD (mV) 3080f 4 CURRENT LIMIT (A) UW TYPICAL PERFOR A CE CHARACTERISTICS MINIMUM CONTROL VOLTAGE (VCONTROL – VOUT) (V) MINIMUM IN VOLTAGE (VIN – VOUT) (mV) Dropout Voltage (Minimum IN Voltage) 400 350 ILOAD = 1.1A 300 250 200 ILOAD = 500mA 150 100 ILOAD = 100mA 50 Dropout Voltage (Minimum VCONTROL Pin Voltage) 1.6 TJ = –50°C 1.4 1.2 1.0 TJ = 25°C 0.8 TJ = 125°C 0.6 0.4 0.2 0 –50 –25 0 25 50 75 100 125 150 TEMPERATURE (°C) 3080 G10 0 0 0.2 0.4 0.6 0.8 1.0 1.2 OUTPUT CURRENT (A) 3080 G11 LOAD CURRENT (A) OUTPUT VOLTAGE DEVIATION (mV) Current Limit 1.6 1.4 1.2 1.0 VIN = 7V VOUT = 0V 0.8 0.6 0.4 0.2 0 –50 –25 0 25 50 75 100 125 150 TEMPERATURE (°C) 3080 G13 Load Transient Response 150 100 50 0 –50 –100 1.2 0.9 VIN = VCONTROL = 3V VOUT = 1.5V 0.6 COUT = 10μF CERAMIC CSET = 0.1μF 0.3 0 0 5 10 15 20 25 30 35 40 45 50 TIME (μs) 3080 G16 IN/CONTROL VOLTAGE (V) OUTPUT VOLTAGE DEVIATION (mV) CURRENT LIMIT (A) Current Limit 1.6 TJ = 25°C 1.4 SOT-223 1.2 AND TO-220 1.0 0.8 0.6 MSOP 0.4 AND DFN 0.2 0 0 6 12 18 24 30 36* INPUT-TO-OUTPUT DIFFERENTIAL (V) *SEE NOTE 9 IN ELECTRICAL CHARACTERISTICS TABLE 3080 G14 Line Transient Response 75 50 25 0 –25 –50 VOUT = 1.5V ILOAD = 10mA 6 COUT = 2.2μF CERAMIC 5 CSET = 0.1μF 4 CERAMIC 3 2 0 10 20 30 40 50 60 70 80 90 100 TIME (μs) 3080 G17 OUTPUT VOLTAGE (V) INPUT VOLTAGE (V) LOAD CURRENT (mA) OUTPUT VOLTAGE DEVIATION (mV) MINIMUM CONTROL VOLTAGE (VCONTROL – VOUT) (V) LT3080 Dropout Voltage (Minimum VCONTROL Pin Voltage) 1.6 1.4 ILOAD = 1.1A 1.2 1.0 ILOAD = 1mA 0.8 0.6 0.4 0.2 0 –50 –25 0 25 50 75 100 125 150 TEMPERATURE (°C) 3080 G12 Load Transient Response 75 VOUT = 1.5V 50 CSET = 0.1μF 25 VIN = VCONTROL = 3V 0 –25 COUT = 10μF CERAMIC –50 COUT = 2.2μF CERAMIC 400 300 200 100 0 0 5 10 15 20 25 30 35 40 45 50 TIME (μs) 3080 G15 Turn-On Response 5 4 3 2 1 0 2.0 COUT = 2.2μF CERAMIC 1.5 1.0 RSET = 100k 0.5 CSET = 0 0 RLOAD = 1Ω 0 1 2 3 4 5 6 7 8 9 10 TIME (μs) 3080 G27 3080f 5 CONTROL PIN CURRENT (mA) CONTROL PIN CURRENT (mA) OUTPUT VOLTAGE (V) LT3080 TYPICAL PERFOR A CE CHARACTERISTICS UW VCONTROL Pin Currrent 25 20 ILOAD = 1.1A DEVICE IN CURRENT LIMIT 15 10 5 ILOAD = 1mA 0 0 6 12 18 24 30 36* INPUT-TO-OUTPUT DIFFERENTIAL (V) *SEE NOTE 9 IN ELECTRICAL CHARACTERISTICS TABLE 3080 G18 Ripple Rejection - Single Supply 100 VIN = VCONTROL = VOUT (NOMINAL) + 2V 90 80 RIPPLE = 50mVP–P 70 ILOAD = 100mA ILOAD = 1.1A 60 50 40 30 20 10 COUT = 2.2μF CERAMIC 0 10 100 1k 10k 100k 1M FREQUENCY (Hz) 3080 G21 RIPPLE REJECTION (dB) VCONTROL Pin Current 30 VCONTROL – VOUT = 2V VIN – VOUT = 1V 25 20 TJ = –50°C 15 10 TJ = 25°C 5 TJ = 125°C 0 0 0.2 0.4 0.6 0.8 1.0 1.2 LOAD CURRENT (A) 3080 G19 Ripple Rejection - Dual Supply - VCONTROL Pin 100 90 80 70 ILOAD = 100mA ILOAD = 1.1A 60 50 40 VIN = VOUT (NOMINAL) + 1V 30 VCONTROL = VOUT (NOMINAL) +2V 20 COUT = 2.2μF CERAMIC 10 RIPPLE = 50mVP–P 0 10 100 1k 10k 100k 1M FREQUENCY (Hz) 3080 G22 RIPPLE REJECTION (dB) RIPPLE REJECTION (dB) Residual Output Voltage with Less Than Minimum Load 0.8 SET PIN = 0V 0.7 VIN 0.6 VOUT RTEST VIN = 20V 0.5 0.4 VIN = 10V 0.3 VIN = 5V 0.2 0.1 0 0 1k 2k RTEST (Ω) 3080 G20 Ripple Rejection - Dual Supply - IN Pin 100 90 80 70 60 50 40 VIN = VOUT (NOMINAL) + 1V 30 VCONTROL = VOUT (NOMINAL) +2V RIPPLE = 50mVP–P 20 10 COUT = 2.2μF CERAMIC ILOAD = 1.1A 0 10 100 1k 10k 100k 1M FREQUENCY (Hz) 3080 G23 RIPPLE REJECTION (dB) REFERENCE CURRENT NOISE SPECTRAL DENSITY (pA/ √Hz) Ripple Rejection (120Hz) 80 79 78 77 76 75 74 73 72 71 70 –50 –25 SINGLE SUPPLY OPERATION VIN = VOUT(NOMINAL) + 2V RIPPLE = 500mVP-P, f=120Hz ILOAD = 1.1A CSET = 0.1μF, COUT = 2.2μF 0 25 50 75 100 125 150 TEMPERATURE (°C) 3080 G24 ERROR AMPLIFIER NOISE SPECTRAL DENSITY (nV/√Hz) Noise Spectral Density 10k 1k 1k 100 100 10 10 1.0 1 0.1 10 100 1k 10k 100k FREQUENCY (Hz) 3080 G25 3080f 6 U UU UW LT3080 TYPICAL PERFOR A CE CHARACTERISTICS PHASE (DEGREES) Output Voltage Noise VOUT 100μV/DIV VOUT = 1V RSET = 100k CSET = O.1μF COUT = 10μF ILOAD = 1.1A TIME 1ms/DIV 3080 G26 GAIN (dB) Error Amplifier Gain and Phase 20 300 15 250 10 200 5 IL = 1.1A 150 0 100 –5 IL = 100mA 50 –10 IL = 1.1A 0 –15 –50 IL = 100mA –20 –100 –25 –150 –30 10 100 1k 10k 100k FREQUENCY (Hz) –200 1M 3080 G28 PI FU CTIO S (DD/MS8E/T/ST) VCONTROL (Pin 5/Pin 5/Pin 4/NA): This pin is the supply pin for the control circuitry of the device. The current flow into this pin is about 1.7% of the output current. For the device to regulate, this voltage must be more than 1.2V to 1.35V greater than the output voltage (see Dropout specifications). IN (Pins 7, 8/Pins 7, 8/Pin 5/Pin 3): This is the collector to the power device of the LT3080. The output load current is supplied through this pin. For the device to regulate, the voltage at this pin must be more than 0.1V to 0.5V greater than the output voltage (see Dropout specifications). NC (Pin 6/Pin 6/Pin 1/NA): No Connection. No Connect pins have no connection to internal circuitry and may be tied to VIN, VCONTROL, VOUT, GND, or floated. OUT (Pins 1-3/Pins 1-3/Pin 3/Pin 2): This is the power output of the device. There must be a minimum load current of 1mA or the output may not regulate. SET(Pin 4/Pin 4/Pin 2/Pin 1): This pin is the input to the error amplifier and the regulation set point for the device. A fixed current of 10μA flows out of this pin through a single external resistor, which programs the output voltage of the device. Output voltage range is zero to the absolute maximum rated output voltage. Transient performance can be improved by adding a small capacitor from the SET pin to ground. Exposed Pad (Pin 9/Pin 9/NA/NA): OUT on MS8E and DFN packages. TAB: OUT on TO-220 and SOT-223 packages. 3080f 7 U W UU W LT3080 BLOCK DIAGRA IN VCONTROL 10μA + – SET 3080 BD OUT APPLICATIO S I FOR ATIO The LT3080 regulator is easy to use and has all the protection features expected in high performance regulators. Included are short-circuit protection and safe operating area protection, as well as thermal shutdown. The LT3080 is especially well suited to applications needing multiple rails. The new architecture adjusts down to zero with a single resistor handling modern low voltage digital IC’s as well as allowing easy parallel operation and thermal management without heat sinks. Adjusting to “zero” output allows shutting off the powered circuitry and when the input is pre-regulated – such as a 5V or 3.3V input supply – external resistors can help spread the heat. A precision “0” TC 10μA internal current source is connected to the non-inverting input of a power operational amplifier. The power operational amplifier provides a low impedance buffered output to the voltage on the non-inverting input. A single resistor from the non-inverting input to ground sets the output voltage and if this resistor is set to zero, zero output results. As can be seen, any output voltage can be obtained from zero up to the maximum defined by the input power supply. What is not so obvious from this architecture are the benefits of using a true internal current source as the reference as opposed to a bootstrapped reference in older regulators. A true current source allows the regulator to have gain and frequency response independent of the impedance on the positive input. Older adjustable regulators, such as the 8 LT1086 have a change in loop gain with output voltage as well as bandwidth changes when the adjustment pin is bypassed to ground. For the LT3080, the loop gain is unchanged by changing the output voltage or bypassing. Output regulation is not fixed at a percentage of the output voltage but is a fixed fraction of millivolts. Use of a true current source allows all the gain in the buffer amplifier to provide regulation and none of that gain is needed to amplify up the reference to a higher output voltage. The LT3080 has the collector of the output transistor connected to a separate pin from the control input. Since the dropout on the collector (IN pin) is only 300mV, two supplies can be used to power the LT3080 to reduce dissipation: a higher voltage supply for the control circuitry and a lower voltage supply for the collector. This increases efficiency and reduces dissipation. To further spread the heat, a resistor can be inserted in series with the collector to move some of the heat out of the IC and spread it on the PC board. The LT3080 can be operated in two modes. Three terminal mode has the control pin connected to the power input pin which gives a limitation of 1.35V dropout. Alternatively, the “control” pin can be tied to a higher voltage and the power IN pin to a lower voltage giving 300mV dropout on the IN pin and minimizing the power dissipation. This allows for a 1.1A supply regulating from 2.5VIN to 1.8VOUT or 1.8VIN to 1.2VOUT with low dissipation. 3080f LT3080 U W UU APPLICATIO S I FOR ATIO IN VCONTROL LT3080 ++ VIN VCONTROL + – SET RSET CSET OUT VOUT COUT 3080 F01 Figure 1. Basic Adjustable Regulator Output Voltage The LT3080 generates a 10μA reference current that flows out of the SET pin. Connecting a resistor from SET to ground generates a voltage that becomes the reference point for the error amplifier (see Figure 1). The reference voltage is a straight multiplication of the SET pin current and the value of the resistor. Any voltage can be generated and there is no minimum output voltage for the regulator. A minimum load current of 1mA is required to maintain regulation regardless of output voltage. For true zero voltage output operation, this 1mA load current must be returned to a negative supply voltage. With the low level current used to generate the reference voltage, leakage paths to or from the SET pin can create errors in the reference and output voltages. High quality insulation should be used (e.g., Teflon, Kel-F); cleaning of all insulating surfaces to remove fluxes and other residues will probably be required. Surface coating may be necessary to provide a moisture barrier in high humidity environments. Board leakage can be minimized by encircling the SET pin and circuitry with a guard ring operated at a potential close to itself; the guard ring should be tied to the OUT pin. Guarding both sides of the circuit board is required. Bulk leakage reduction depends on the guard ring width. Ten nanoamperes of leakage into or out of the SET pin and associated circuitry creates a 0.1% error in the reference voltage. Leakages of this magnitude, coupled with other sources of leakage, can cause significant offset voltage and reference drift, especially over the possible operating temperature range. If guardring techniques are used, this bootstraps any stray capacitance at the SET pin. Since the SET pin is a high impedance node, unwanted signals may couple into the SET pin and cause erratic behavior. This will be most noticeable when operating with minimum output capacitors at full load current. The easiest way to remedy this is to bypass the SET pin with a small amount of capacitance from SET to ground, 10pF to 20pF is sufficient. Stability and Output Capacitance The LT3080 requires an output capacitor for stability. It is designed to be stable with most low ESR capacitors (typically ceramic, tantalum or low ESR electrolytic). A minimum output capacitor of 2.2μF with an ESR of 0.5Ω or less is recommended to prevent oscillations. Larger values of output capacitance decrease peak deviations and provide improved transient response for larger load current changes. Bypass capacitors, used to decouple individual components powered by the LT3080, increase the effective output capacitor value. For improvement in transient performance, place a capacitor across the voltage setting resistor. Capacitors up to 1μF can be used. This bypass capacitor reduces system noise as well, but start-up time is proportional to the time constant of the voltage setting resistor (RSET in Figure 1) and SET pin bypass capacitor. Extra consideration must be given to the use of ceramic capacitors. Ceramic capacitors are manufactured with a variety of dielectrics, each with different behavior across temperature and applied voltage. The most common dielectrics used are specified with EIA temperature characteristic codes of Z5U, Y5V, X5R and X7R. The Z5U and Y5V dielectrics are good for providing high capacitances in a small package, but they tend to have strong voltage and temperature coefficients as shown in Figures 2 and 3. When used with a 5V regulator, a 16V 10μF Y5V capacitor can exhibit an effective value as low as 1μF to 2μF for the DC bias voltage applied and over the operating temperature range. The X5R and X7R dielectrics result in more stable characteristics and are more suitable for use as the output capacitor. The X7R type has better stability across temperature, while the X5R is less expensive and is avail- 3080f 9 LT3080 U W UU CHANGE IN VALUE (%) APPLICATIO S I FOR ATIO 20 BOTH CAPACITORS ARE 16V, 1210 CASE SIZE, 10μF 0 X5R –20 –40 –60 Y5V –80 –100 0 2 4 6 8 10 12 14 16 DC BIAS VOLTAGE (V) 3080 F02 Figure 2. Ceramic Capacitor DC Bias Characteristics 40 20 CHANGE IN VALUE (%) 0 X5R –20 –40 Y5V –60 –80 BOTH CAPACITORS ARE 16V, 1210 CASE SIZE, 10μF –100 –50 –25 0 25 50 75 TEMPERATURE (°C) 100 125 3080 F03 Figure 3. Ceramic Capacitor Temperature Characteristics able in higher values. Care still must be exercised when using X5R and X7R capacitors; the X5R and X7R codes only specify operating temperature range and maximum capacitance change over temperature. Capacitance change due to DC bias with X5R and X7R capacitors is better than Y5V and Z5U capacitors, but can still be significant enough to drop capacitor values below appropriate levels. Capacitor DC bias characteristics tend to improve as component case size increases, but expected capacitance at operating voltage should be verified. Voltage and temperature coefficients are not the only sources of problems. Some ceramic capacitors have a piezoelectric response. A piezoelectric device generates voltage across its terminals due to mechanical stress, similar to the way a piezoelectric microphone works. For a 10 ceramic capacitor the stress can be induced by vibrations in the system or thermal transients. Paralleling Devices LT3080’s may be paralleled to obtain higher output current. The SET pins are tied together and the IN pins are tied together. This is the same whether it’s in three terminal mode or has separate input supplies. The outputs are connected in common using a small piece of PC trace as a ballast resistor to equalize the currents. PC trace resistance in milliohms/inch is shown in Table 1. Only a tiny area is needed for ballasting. Table 1. PC Board Trace Resistance WEIGHT (oz) 10 mil WIDTH 1 54.3 2 27.1 Trace resistance is measured in mOhms/in 20 mil WIDTH 27.1 13.6 The worse case offset between the set pin and the output of only ± 2 millivolts allows very small ballast resistors to be used. As shown in Figure 4, the two devices have a small 10 milliohm ballast resistor, which at full output current gives better than 80 percent equalized sharing of the current. The external resistance of 10 milliohms (5 VIN 4.8V TO 28V 1μF VIN VCONTROL LT3080 + – SET OUT 10mΩ VIN VCONTROL LT3080 + – SET 165k OUT 10mΩ VOUT 3.3V 2A 10μF 3080 F04 Figure 4. Parallel Devices 3080f LT3080 U W UU APPLICATIO S I FOR ATIO milliohms for the two devices in parallel) only adds about 10 millivolts of output regulation drop at an output of 2A. Even with an output voltage as low as 1V, this only adds 1% to the regulation. Of course, more than two LT3080’s can be paralleled for even higher output current. They are spread out on the PC board, spreading the heat. Input resistors can further spread the heat if the input-to-output difference is high. Thermal Performance In this example, two LT3080 3mm × 3mm DFN devices are mounted on a 1oz copper 4-layer PC board. They are placed approximately 1.5 inches apart and the board is mounted vertically for convection cooling. Two tests were set up to measure the cooling performance and current sharing of these devices. The first test was done with approximately 0.7V inputto-output and 1A per device. This gave a 700 milliwatt dissipation in each device and a 2A output current. The temperature rise above ambient is approximately 28°C and both devices were within plus or minus 1°C. Both the thermal and electrical sharing of these devices is excellent. The thermograph in Figure 5 shows the temperature distribution between these devices and the PC board reaches ambient temperature within about a half an inch from the devices. The power is then increased with 1.7V across each device. This gives 1.7 watts dissipation in each device and a device temperature of about 90°C, about 65°C above ambient as shown in Figure 6. Again, the temperature matching between the devices is within 2°C, showing excellent tracking between the devices. The board temperature has reached approximately 40°C within about 0.75 inches of each device. While 90°C is an acceptable operating temperature for these devices, this is in 25°C ambient. For higher ambients, the temperature must be controlled to prevent device temperature from exceeding 125°C. A 3-meter-per-second airflow across the devices will decrease the device temperature about 20°C providing a margin for higher operating ambient temperatures. Both at low power and relatively high power levels devices can be paralleled for higher output current. Current sharing and thermal sharing is excellent, showing that acceptable operation can be had while keeping the peak temperatures below excessive operating temperatures on a board. This technique allows higher operating current linear regulation to be used in systems where it could never be used before. Quieting the Noise The LT3080 offers numerous advantages when it comes to dealing with noise. There are several sources of noise in a linear regulator. The most critical noise source for any LDO is the reference; from there, the noise contribution Figure 5. Temperature Rise at 700mW Dissipation Figure 6. Temperature Rise at 1.7W Dissipation 3080f 11 LT3080 U W UU APPLICATIO S I FOR ATIO from the error amplifier must be considered, and the gain created by using a resistor divider cannot be forgotten. Traditional low noise regulators bring the voltage reference out to an external pin (usually through a large value resistor) to allow for bypassing and noise reduction of reference noise. The LT3080 does not use a traditional voltage reference like other linear regulators, but instead uses a reference current. That current operates with typical noise current levels of 3.2pA/√⎯Hz (1nARMS over the 10Hz to 100kHz bandwidth). The voltage noise of this is equal to the noise current multiplied by the resistor value. The resistor generates spot noise equal to √⎯4⎯k⎯T⎯R (k = Boltzmann’s constant, 1.38 • 10-23 J/°K, and T is absolute temperature) which is RMS summed with the reference current noise. To lower reference noise, the voltage setting resistor may be bypassed with a capacitor, though this causes start-up time to increase as a factor of the RC time constant. The LT3080 uses a unity-gain follower from the SET pin to drive the output, and there is no requirement to use a resistor to set the output voltage. Use a high accuracy voltage reference placed at the SET pin to remove the errors in output voltage due to reference current tolerance and resistor tolerance. Active driving of the SET pin is acceptable; the limitations are the creativity and ingenuity of the circuit designer. One problem that a normal linear regulator sees with reference voltage noise is that noise is gained up along with the output when using a resistor divider to operate at levels higher than the normal reference voltage. With the LT3080, the unity-gain follower presents no gain whatsoever from the SET pin to the output, so noise figures do not increase accordingly. Error amplifier noise is typically 125nV/√⎯Hz (40μVRMS over the 10Hz to 100kHz bandwidth); this is another factor that is RMS summed in to give a final noise figure for the regulator. Curves in the Typical Performance Characteristics show noise spectral density and peak-to-peak noise characteristics for both the reference current and error amplifier over the 10Hz to 100kHz bandwidth. Overload Recovery Like many IC power regulators, the LT3080 has safe operating area (SOA) protection. The SOA protection decreases 12 current limit as the input-to-output voltage increases and keeps the power dissipation at safe levels for all values of input-to-output voltage. The LT3080 provides some output current at all values of input-to-output voltage up to the device breakdown. See the Current Limit curve in the Typical Performance Characteristics. When power is first turned on, the input voltage rises and the output follows the input, allowing the regulator to start into very heavy loads. During start-up, as the input voltage is rising, the input-to-output voltage differential is small, allowing the regulator to supply large output currents. With a high input voltage, a problem can occur wherein removal of an output short will not allow the output voltage to recover. Other regulators, such as the LT1085 and LT1764A, also exhibit this phenomenon so it is not unique to the LT3080. The problem occurs with a heavy output load when the input voltage is high and the output voltage is low. Common situations are immediately after the removal of a short circuit. The load line for such a load may intersect the output current curve at two points. If this happens, there are two stable operating points for the regulator. With this double intersection, the input power supply may need to be cycled down to zero and brought up again to make the output recover. Load Regulation Because the LT3080 is a floating device (there is no ground pin on the part, all quiescent and drive current is delivered to the load), it is not possible to provide true remote load sensing. Load regulation will be limited by the resistance IN VCONTROL LT3080 + – SET RSET PARASITIC RESISTANCE OUT RP RP LOAD RP 3080 F07 Figure 7. Connections for Best Load Regulation 3080f LT3080 U W UU APPLICATIO S I FOR ATIO of the connections between the regulator and the load. The data sheet specification for load regulation is Kelvin sensed at the pins of the package. Negative side sensing is a true Kelvin connection, with the bottom of the voltage setting resistor returned to the negative side of the load (see Figure 7). Connected as shown, system load regulation will be the sum of the LT3080 load regulation and the parasitic line resistance multiplied by the output current. It is important to keep the positive connection between the regulator and load as short as possible and use large wire or PC board traces. surements were taken in still air on two-sided 1/16” FR-4 board with one ounce copper. Table 2. MSE Package, 8-Lead MSOP COPPER AREA TOPSIDE* BACKSIDE BOARD AREA 2500mm2 1000mm2 225mm2 100mm2 2500mm2 2500mm2 2500mm2 2500mm2 2500mm2 2500mm2 2500mm2 2500mm2 *Device is mounted on topside THERMAL RESISTANCE (JUNCTION-TO-AMBIENT) 55°C/W 57°C/W 60°C/W 65°C/W Thermal Considerations The LT3080 has internal power and thermal limiting circuitry designed to protect it under overload conditions. For continuous normal load conditions, maximum junction temperature must not be exceeded. It is important to give consideration to all sources of thermal resistance from junction to ambient. This includes junction-to-case, case-to-heat sink interface, heat sink resistance or circuit board-to-ambient as the application dictates. Additional heat sources nearby must also be considered. For surface mount devices, heat sinking is accomplished by using the heat spreading capabilities of the PC board and its copper traces. Surface mount heat sinks and plated through-holes can also be used to spread the heat generated by power devices. Junction-to-case thermal resistance is specified from the IC junction to the bottom of the case directly below the die. This is the lowest resistance path for heat flow. Proper mounting is required to ensure the best possible thermal flow from this area of the package to the heat sinking material. For the TO-220 package, thermal compound is strongly recommended for mechanical connections to a heat sink. A thermally conductive spacer can be used for electrical isolation as long as the added contribution to thermal resistance is considered. Note that the Tab or Exposed Pad (depending on package) is electrically connected to the output. The following tables list thermal resistance for several different copper areas given a fixed board size. All mea- Table 3. DD Package, 8-Lead DFN COPPER AREA TOPSIDE* BACKSIDE BOARD AREA 2500mm2 2500mm2 2500mm2 1000mm2 2500mm2 2500mm2 225mm2 100mm2 2500mm2 2500mm2 2500mm2 2500mm2 *Device is mounted on topside THERMAL RESISTANCE (JUNCTION-TO-AMBIENT) 60°C/W 62°C/W 65°C/W 68°C/W Table 4. ST Package, 3-Lead SOT-223 COPPER AREA TOPSIDE* 2500mm2 1000mm2 225mm2 BACKSIDE 2500mm2 2500mm2 2500mm2 BOARD AREA 2500mm2 2500mm2 2500mm2 100mm2 2500mm2 2500mm2 *Device is mounted on topside THERMAL RESISTANCE (JUNCTION-TO-AMBIENT) 48°C/W 48°C/W 56°C/W 62°C/W T Package, 5-Lead TO-220 Thermal Resistance (Junction-to-Case) = 3°C/W Calculating Junction Temperature Example: Given an output voltage of 0.9V, a VCONTROL voltage of 3.3V ±10%, an IN voltage of 1.5V ±5%, output current range from 1mA to 1A and a maximum ambient temperature of 50°C, what will the maximum junction temperature be for the DFN package on a 2500mm2 board with topside copper area of 500mm2? 3080f 13 LT3080 U W UU APPLICATIO S I FOR ATIO The power in the drive circuit equals: PDRIVE = (VCONTROL – VOUT)(ICONTROL) where ICONTROL is equal to IOUT/60. ICONTROL is a function of output current. A curve of ICONTROL vs IOUT can be found in the Typical Performance Characteristics curves. The power in the output transistor equals: POUTPUT = (VIN – VOUT)(IOUT) The total power equals: PTOTAL = PDRIVE + POUTPUT The current delivered to the SET pin is negligible and can be ignored. VCONTROL(MAX CONTINUOUS) = 3.630V (3.3V + 10%) VIN(MAX CONTINUOUS) = 1.575V (1.5V + 5%) VOUT = 0.9V, IOUT = 1A, TA = 50°C Power dissipation under these conditions is equal to: PDRIVE = (VCONTROL – VOUT)(ICONTROL) ICONTROL = IOUT 60 = 1A 60 = 17mA PDRIVE = (3.630V – 0.9V)(17mA) = 46mW POUTPUT = (VIN – VOUT)(IOUT) POUTPUT = (1.575V – 0.9V)(1A) = 675mW Total Power Dissipation = 721mW C1 VCONTROL LT3080 + – SET RSET VIN RS IN VINʹ OUT VOUT C2 3080 F08 Junction Temperature will be equal to: TJ = TA + PTOTAL • θJA (approximated using tables) TJ = 50°C + 721mW • 64°C/W = 96°C In this case, the junction temperature is below the maximum rating, ensuring reliable operation. Reducing Power Dissipation In some applications it may be necessary to reduce the power dissipation in the LT3080 package without sacrificing output current capability. Two techniques are available. The first technique, illustrated in Figure 8, employs a resistor in series with the regulator’s input. The voltage drop across RS decreases the LT3080’s IN-to-OUT differential voltage and correspondingly decreases the LT3080’s power dissipation. As an example, assume: VIN = VCONTROL = 5V, VOUT = 3.3V and IOUT(MAX) = 1A. Use the formulas from the Calculating Junction Temperature section previously discussed. Without series resistor RS, power dissipation in the LT3080 equals: PTOTAL = (5V – 3.3V ) •   1A 60   + (5V – 3.3V ) • 1A = 1.73W If the voltage differential (VDIFF) across the NPN pass transistor is chosen as 0.5V, then RS equals: RS = 5V – 3.3V 1A − 0.5V = 1.2Ω Power dissipation in the LT3080 now equals: PTOTAL = (5V – 3.3V ) •   1A 60   + (0.5V) • 1A = 0.53W The LT3080’s power dissipation is now only 30% compared to no series resistor. RS dissipates 1.2W of power. Choose appropriate wattage resistors to handle and dissipate the power properly. Figure 8. Reducing Power Dissipation Using a Series Resistor 3080f 14 LT3080 U W UU APPLICATIO S I FOR ATIO The second technique for reducing power dissipation, shown in Figure 9, uses a resistor in parallel with the LT3080. This resistor provides a parallel path for current flow, reducing the current flowing through the LT3080. This technique works well if input voltage is reasonably constant and output load current changes are small. This technique also increases the maximum available output current at the expense of minimum load requirements. As an example, assume: VIN = VCONTROL = 5V, VIN(MAX) = 5.5V, VOUT = 3.3V, VOUT(MIN) = 3.2V, IOUT(MAX) = 1A and IOUT(MIN) = 0.7A. Also, assuming that RP carries no more than 90% of IOUT(MIN) = 630mA. Calculating RP yields: RP = 5.5V – 3.2V 0.63A = 3.65Ω (5% Standard value = 3.6Ω) The maximum total power dissipation is (5.5V – 3.2V) • 1A = 2.3W. However the LT3080 supplies only: 1A – 5.5V – 3.2V 3.6Ω = 0.36A Therefore, the LT3080’s power dissipation is only: PDIS = (5.5V – 3.2V) • 0.36A = 0.83W RP dissipates 1.47W of power. As with the first technique, choose appropriate wattage resistors to handle and dissipate the power properly. With this configuration, the LT3080 supplies only 0.36A. Therefore, load current can increase by 0.64A to 1.64A while keeping the LT3080 in its normal operating range. VIN C1 VCONTROL LT3080 IN + – SET RSET RP OUT VOUT C2 3080 F09 Figure 9. Reducing Power Dissipation Using a Parallel Resistor 3080f 15 LT3080 U TYPICAL APPLICATIO S Higher Output Current VIN MJ4502 6V 50Ω IN LT3080 + 100μF VCONTROL 1μF + – SET 332k OUT VOUT 3.3V + 5A 4.7μF 100μF 3080 TA02 ON OFF Current Source Adding Shutdown IN VIN VCONTROL LT3080 + – SET Q1 VN2222LL R1 SHUTDOWN 3080 TA04 OUT VOUT Q2* VN2222LL *Q2 INSURES ZERO OUTPUT IN THE ABSENCE OF ANY OUTPUT LOAD. VIN IN 10V VCONTROL 1μF LT3080 + – SET 100k OUT 1Ω IOUT 0A TO 1A 4.7μF 3080 TA03 Low Dropout Voltage LED Driver C1 VCONTROL LT3080 D1 IN VIN 100mA + – SET R1 24.9k OUT R2 2.49Ω 3080 TA05 3080f 16 LT3080 U TYPICAL APPLICATIO S Using a Lower Value SET Resistor VIN IN 12V VCONTROL C1 1μF LT3080 + – SET R1 49.9k 1% RSET 10k OUT R2 1mA 499Ω 1% VOUT 0.5V TO 10V COUT 4.7μF VOUT = 0.5V + 1mA • RSET 3080 TA06 Adding Soft-Start VIN 4.8V to 28V IN VCONTROL C1 D1 1μF 1N4148 C2 0.01μF LT3080 + – SET R1 332k OUT VOUT 3.3V 1A COUT 4.7μF 3080 TA07 VIN 7V TO 28V IN VCONTROL C1 1.5μF LT3080 + – SET R1 249k Coincident Tracking IN VCONTROL IN LT3080 VCONTROL + – OUT SET R2 OUT 80.6k VOUT1 2.5V 1A C2 4.7μF LT3080 + – SET 169k VOUT2 3.3V C3 4.7μF OUT VOUT3 5V 4.7μF 3080 TA08 3080f 17 LT3080 TYPICAL APPLICATIO S U Lab Supply VIN 12V TO 18V IN VCONTROL + 15μF LT3080 + – SET IN VCONTROL OUT 1Ω 100k 0A TO 1A + 15μF LT3080 + – SET R4 1MEG OUT 4.7μF VOUT 0V TO 10V + 100μF 3080 TA09 High Voltage Regulator VIN 10k 50V BUZ11 + 10μF 1N4148 IN VCONTROL + 15μF 6.1V LT3080 + – SET RSET 2MEG OUT 4.7μF VOUT 1A VOUT = 20V VOUT = 10μA • RSET 3080 TA10 Ramp Generator VIN IN LT3080 5V VCONTROL 1μF + – VN2222LL SET 1μF OUT VN2222LL VOUT 4.7μF 3080 TA12 3080f 18 U TYPICAL APPLICATIO S Reference Buffer IN VIN VCONTROL INPUT LT1019 OUTPUT GND LT3080 + – SET C1 1μF OUT VOUT* C2 4.7μF 3080 TA11 *MIN LOAD 0.5mA Ground Clamp IN VIN VCONTROL 1μF LT3080 VEXT + – OUT 1N4148 5k 20Ω VOUT 4.7μF 3080 TA13 Boosting Fixed Output Regulators LT3080 + – 5V 10μF LT1963-3.3 SET 20mΩ 42Ω* 33k *4mV DROP ENSURES LT3080 IS OFF WITH NO LOAD MULTIPLE LT3080’S CAN BE USED OUT 20mΩ 3.3VOUT 2.6A 47μF 3080 TA20 LT3080 3080f 19 U LT3080 TYPICAL APPLICATIO S Low Voltage, High Current Adjustable High Efficiency Regulator* 2.7V TO 5.5V† 2× + 100μF PVIN SW SVIN ITH 2.2MEG 100k LTC3414 RT PGOOD RUN/SS 1000pF VFB SYNC/MODE SGND PGND 0.47μH 12.1k 294k 78.7k 124k + 470pF 2× 100μF 2N3906 *DIFFERENTIAL VOLTAGE ON LT3080 IS 0.6V SET BY THE VBE OF THE 2N3906 PNP. †MAXIMUM OUTPUT VOLTAGE IS 1.5V BELOW INPUT VOLTAGE 10k IN VCONTROL LT3080 + – SET IN LT3080 VCONTROL + – SET OUT 20mΩ OUT 20mΩ 0V TO 4V† 4A IN VCONTROL LT3080 + – SET OUT 20mΩ IN LT3080 VCONTROL + – SET 100k OUT 20mΩ 3080 TA18 + 100μF 3080f 20 U TYPICAL APPLICATIO S Adjustable High Efficiency Regulator* LT3080 CMDSH-4E 4.5V TO 25V† 10μF 1μF 0.1μF VIN BOOST 100k LT3493 SHDN SW 0.1μF 10μH MBRM140 FB GND 10k 68μF TP0610L *DIFFERENTIAL VOLTAGE ON LT3080 ≈ 1.4V SET BY THE TPO610L P-CHANNEL THRESHOLD. †MAXIMUM OUTPUT VOLTAGE IS 2V BELOW INPUT VOLTAGE IN LT3080 VCONTROL + – SET 1MEG 10k OUT 3080 TA19 0V TO 10V† 1A 4.7μF 2 Terminal Current Source CCOMP* IN VCONTROL LT3080 + – SET 100k *CCOMP R1 ≤ 10Ω 10μF R1 ≥ 10Ω 2.2μF R1 3080 TA21 IOUT = 1V R1 3080f 21 LT3080 U PACKAGE DESCRIPTIO DD Package 8-Lead Plastic DFN (3mm × 3mm) (Reference LTC DWG # 05-08-1698) 0.675 ±0.05 R = 0.115 TYP 5 0.38 ± 0.10 8 3.5 ±0.05 1.65 ±0.05 2.15 ±0.05 (2 SIDES) PIN 1 PACKAGE TOP MARK OUTLINE (NOTE 6) 0.25 ± 0.05 0.50 BSC 2.38 ±0.05 (2 SIDES) 0.200 REF RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS NOTE: 1. DRAWING TO BE MADE A JEDEC PACKAGE OUTLINE M0-229 VARIATION OF (WEED-1) 2. DRAWING NOT TO SCALE 3. ALL DIMENSIONS ARE IN MILLIMETERS 4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE 5. EXPOSED PAD SHALL BE SOLDER PLATED 6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION ON TOP AND BOTTOM OF PACKAGE 3.00 ±0.10 (4 SIDES) 1.65 ± 0.10 (2 SIDES) 0.75 ±0.05 0.00 – 0.05 4 0.25 ± 0.05 (DD8) DFN 1203 1 0.50 BSC 2.38 ±0.10 (2 SIDES) BOTTOM VIEW—EXPOSED PAD MS8E Package 8-Lead Plastic MSOP (Reference LTC DWG # 05-08-1662) BOTTOM VIEW OF EXPOSED PAD OPTION 2.06 ± 0.102 1 (.081 ± .004) 1.83 ± 0.102 (.072 ± .004) 0.254 (.010) DETAIL “A” 0° – 6° TYP 3.00 ± 0.102 (.118 ± .004) (NOTE 3) 8 7 65 0.52 (.0205) REF 4.90 ± 0.152 (.193 ± .006) 3.00 ± 0.102 (.118 ± .004) (NOTE 4) 8 2.794 ± 0.102 (.110 ± .004) 0.889 ± 0.127 (.035 ± .005) 5.23 (.206) MIN 2.083 ± 0.102 3.20 – 3.45 (.082 ± .004) (.126 – .136) 0.42 ± 0.038 (.0165 ± .0015) TYP 0.65 (.0256) BSC RECOMMENDED SOLDER PAD LAYOUT GAUGE PLANE 0.18 (.007) 0.53 ± 0.152 (.021 ± .006) DETAIL “A” 1 234 1.10 (.043) MAX 0.86 (.034) REF SEATING PLANE 0.22 – 0.38 NOTE: 1. DIMENSIONS IN MILLIMETER/(INCH) 2. DRAWING NOT TO SCALE (.009 – .015) TYP 0.65 (.0256) BSC 3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS. MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS. INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX 0.127 ± 0.076 (.005 ± .003) MSOP (MS8E) 0603 3080f 22 U PACKAGE DESCRIPTIO .390 – .415 (9.906 – 10.541) T Package 5-Lead Plastic TO-220 (Standard) (Reference LTC DWG # 05-08-1421) .147 – .155 (3.734 – 3.937) DIA .165 – .180 (4.191 – 4.572) .460 – .500 (11.684 – 12.700) .230 – .270 (5.842 – 6.858) .570 – .620 (14.478 – 15.748) .330 – .370 (8.382 – 9.398) .620 (15.75) TYP .700 – .728 (17.78 – 18.491) LT3080 .045 – .055 (1.143 – 1.397) BSC .067 (1.70) .028 – .038 (0.711 – 0.965) SEATING PLANE .152 – .202 .260 – .320 (3.861 – 5.131) (6.60 – 8.13) .135 – .165 (3.429 – 4.191) .095 – .115 (2.413 – 2.921) .155 – .195* (3.937 – 4.953) .013 – .023 (0.330 – 0.584) * MEASURED AT THE SEAT ST Package 3-Lead Plastic SOT-223 (Reference LTC DWG # 05-08-1630) .248 – .264 (6.30 – 6.71) .114 – .124 (2.90 – 3.15) .059 MAX .129 MAX .264 – .287 (6.70 – 7.30) .130 – .146 (3.30 – 3.71) .248 BSC .039 MAX .0905 (2.30) BSC .059 MAX .033 – .041 (0.84 – 1.04) .090 BSC .181 MAX RECOMMENDED SOLDER PAD LAYOUT .071 (1.80) MAX .024 – .033 (0.60 – 0.84) .181 (4.60) BSC 10° – 16° 10° MAX .012 (0.31) MIN .0008 – .0040 (0.0203 – 0.1016) Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights. .010 – .014 (0.25 – 0.36) 10° – 16° ST3 (SOT-233) 0502 3080f 23 LT3080 U TYPICAL APPLICATIO Paralleling Regulators IN LT3080 VCONTROL + – SET OUT 20mΩ VIN 4.8V TO 28V IN VCONTROL 1μF LT3080 + – SET 165k OUT 20mΩ VOUT 3.3V 2A 10μF 3080 TA14 RELATED PARTS PART NUMBER LDOs LT1086 LT1117 LT1118 LT1963A LT1965 DESCRIPTION 1.5A Low Dropout Regulator 800mA Low Dropout Regulator 800mA Low Dropout Regulator 1.5A Low Noise, Fast Transient Response LDO 1.1A Low Noise LDO LTC®3026 1.5A Low Input Voltage VLDOTM Regulator Switching Regulators LT1976 High Voltage, 1.5A Step-Down Switching Regulator LTC3414 4A (IOUT), 4MHz Synchronous Step-Down DC/DC Converter LTC3406/LTC3406B 600mA (IOUT), 1.5MHz Synchronous Step-Down DC/DC Converter LTC3411 1.25A (IOUT), 4MHz Synchronous Step-Down DC/DC Converter VLDO and ThinSOT are trademarks of Linear Technology Corporation. COMMENTS Fixed 2.85V, 3.3V, 3.6V, 5V and 12V Output 1V Dropout, Adjustable or Fixed Output, DD-Pak, SOT-223 Packages OK for Sinking and Sourcing, S0-8 and SOT-223 Packages 340mV Dropout Voltage, Low Noise: 40μVRMS, VIN = 2.5V to 20V, TO-220, DD, SOT-223 and SO-8 Packages 290mV Dropout Voltage, Low Noise 40μVRMS, VIN = 1.8V to 20V, VOUT = 1.2V to 19.5V, Stable with Ceramic Caps TO-220, DDPak, MSOP and 3mm × 3mm DFN packages. VIN: 1.14V to 3.5V (Boost Enabled), 1.14V to 5.5V (with External 5V), VDO = 0.1V, IQ = 950μA, Stable with 10μF Ceramic Capacitors, 10-Lead MSOP and DFN Packages f = 200kHz, IQ = 100μA, TSSOP-16E Package 95% Efficiency, VIN: 2.25V to 5.5V, VOUT(MIN) = 0.8V, TSSOP Package 95% Efficiency, VIN: 2.5V to 5.5V, VOUT(MIN) = 0.6V, IQ = 20μA, ISD < 1μA, ThinSOTTM Package 95% Efficiency, VIN: 2.5V to 5.5V, VOUT(MIN) = 0.8V, IQ = 60μA, ISD < 1μA, 10-Lead MS or DFN Packages 24 Linear Technology Corporation 1630 McCarthy Blvd., Milpitas, CA 95035-7417 (408) 432-1900 ● FAX: (408) 434-0507 ● www.linear.com 3080f LT 1107 • PRINTED IN USA © LINEAR TECHNOLOGY CORPORATION 2007

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